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FEATURES
s s s s s s s s s s s s s s s s
LT1806/LT1807 325MHz, Single/Dual, Rail-to-Rail Input and Output, Low Distortion, Low Noise Precision Op Amps DESCRIPTIO
The LT(R)1806/LT1807 are single/dual low noise rail-to-rail input and output unity-gain stable op amps that feature a 325MHz gain-bandwidth product, a 140V/s slew rate and a 85mA output current. They are optimized for low voltage, high performance signal conditioning systems. The LT1806/LT1807 have a very low distortion of - 80dBc at 5MHz, a low input referred noise voltage of 3.5nV/Hz and a maximum offset voltage of 550V that allows them to be used in high performance data acquisition systems. The LT1806/LT1807 have an input range that includes both supply rails and an output that swings within 20mV of either supply rail to maximize the signal dynamic range in low supply applications. The LT1806/LT1807 maintain their performance for supplies from 2.5V to 12.6V and are specified at 3V, 5V and 5V supplies. The inputs can be driven beyond the supplies without damage or phase reversal of the output. The LT1806 is available in an 8-pin SO package with the standard op amp pinout and a 6-pin SOT-23 package. The LT1807 features the standard dual op amp pinout and is available in 8-pin SO and MSOP packages.These devices can be used as plug-in replacements for many op amps to improve input/output range and performance.
Gain Bandwidth Product: 325MHz Slew Rate: 140V/s Wide Supply Range: 2.5V to 12.6V Large Output Current: 85mA Low Distortion, 5MHz: -80dBc Low Voltage Noise: 3.5nV/Hz Input Common Mode Range Includes Both Rails Output Swings Rail-to-Rail Input Offset Voltage (Rail-to-Rail): 550V Max Common Mode Rejection: 106dB Typ Power Supply Rejection: 105dB Typ Unity-Gain Stable Power Down Pin (LT1806) Single in SO-8 and 6-Pin SOT-23 Packages Dual in SO-8 and 8-Pin MSOP Packages Operating Temperature Range: -40C to 85C
APPLICATIO S
s s s s s
Low Voltage, High Frequency Signal Processing Driving A/D Converters Rail-to-Rail Buffer Amplifiers Active Filters Video Line Driver
, LTC and LT are registered trademarks of Linear Technology Corporation.
TYPICAL APPLICATIO
+
1/2 LT1807
Gain of 20 Differential A/D Driver
0 -20
AMPLITUDE (dB)
4096 Point FFT Response
VS = 5V AV = 20 fSAMPLE = 10Msps fIN = 1.4086MHz SFDR = 83dB NONAVERAGED VIN = 200mVP-P
-
R2 909 R5 49.9 C3 470pF C2 5.6pF R6 49.9
5V
-40 -60 -80
R1 100 VIN
C1 5.6pF
LTC(R)1420 PGA GAIN = 1 VREF = 4.096V -AVIN
+AVIN
12 BITS 10Msps
-100
18067 TA01
R3 100
- +
R4 1k
-5V
-120 0 1 2 3 FREQUENCY (MHz) 4 5
18067 TA02
1/2 LT1807
U
U
U
1
LT1806/LT1807
ABSOLUTE
AXI U
RATI GS
Total Supply Voltage (V + to V -) ............................ 12.6V Input Voltage (Note 2) ............................................. VS Input Current (Note 2) ........................................ 10mA Output Short-Circuit Duration (Note 3) ............ Indefinite Operating Temperature Range (Note 4) .. - 40C to 85C
PACKAGE/ORDER I FOR ATIO
TOP VIEW OUT 1 V- 2 +IN 3 6 V+ 5 SHDN 4 -IN
ORDER PART NUMBER
SHDN 1
+IN 3 V- 4
S6 PACKAGE 6-LEAD PLASTIC SOT-23
TJMAX = 150C, JA = 160C/W (Note 9)
S6 PART MARKING LTNK LTNL ORDER PART NUMBER
S8 PACKAGE 8-LEAD PLASTIC SO TJMAX = 150C, JA = 100C/W (Note 9)
TOP VIEW OUT A 1 + - 8 7 6 5 + - V+ OUT B -IN B +IN B
TOP VIEW OUT A -IN A +IN A V- 1 2 3 4 8 7 6 5 V+ OUT B -IN B +IN B
LT1807CMS8 LT1807IMS8 MS8 PART MARKING LTTT LTTV
-IN A 2 +IN A 3 V- 4
MS8 PACKAGE 8-LEAD PLASTIC MSOP
TJMAX = 150C, JA = 135C/W (Note 9)
S8 PACKAGE 8-LEAD PLASTIC SO TJMAX = 150C, JA = 100C/W (Note 9)
Consult factory for parts specified with wider operating temperature ranges.
ELECTRICAL CHARACTERISTICS
TA = 25C. VS = 5V, 0V; VS = 3V, 0V; VSHDN = open; VCM = VOUT = half supply, unless otherwise noted.
SYMBOL VOS PARAMETER Input Offset Voltage CONDITIONS VCM = V + VCM = V - VCM = V + (LT1806 SOT-23) VCM = V - (LT1806 SOT-23) VCM = V - to V + VCM = V - to V + (LT1806 SOT-23) VCM = V - to V + VCM = V + VCM = V - + 0.2V VCM = V - to V + VCM = V + VCM = V - + 0.2V MIN TYP 100 100 100 100 50 100 200 1 -5 6 0.03 0.05 MAX 550 550 700 700 550 700 1000 4 17 1.2 3.0 UNITS V V V V V V V A A A A A
VOS
Input Offset Voltage Shift Input Offset Voltage Match (Channel-to-Channel) (Note 10)
IB IB
Input Bias Current Input Bias Current Shift Input Bias Current Match (Channel-to-Channel) (Note 10)
2
+ -
LT1806CS6 LT1806IS6
U
U
W
WW U
W
(Note 1)
Specified Temperature Range (Note 5) ... - 40C to 85C Junction Temperature ........................................... 150C Storage Temperature Range ................. - 65C to 150C Lead Temperature (Soldering, 10 sec).................. 300C
TOP VIEW 8 7 6 5 NC V+ OUT NC
ORDER PART NUMBER LT1806CS8 LT1806IS8 S8 PART MARKING 1806 1806I ORDER PART NUMBER LT1807CS8 LT1807IS8 S8 PART MARKING 1807 1807I
-IN 2
-13
LT1806/LT1807
ELECTRICAL CHARACTERISTICS
TA = 25C. VS = 5V, 0V; VS = 3V, 0V; VSHDN = open; VCM = VOUT = half supply unless otherwise noted.
SYMBOL IOS IOS en in CIN AVOL PARAMETER Input Offset Current Input Offset Current Shift Input Noise Voltage Input Noise Voltage Density Input Noise Current Density Input Capacitance Large-Signal Voltage Gain VS = 5V, VO = 0.5V to 4.5V, RL = 1k to VS/2 VS = 5V, VO = 1V to 4V, RL = 100 to VS/2 VS = 3V, VO = 0.5V to 2.5V, RL = 1k to VS/2 VS = 5V, VCM = V - to V + VS = 3V, VCM = V - to V+ VS = 5V, VCM = V - to V + VS = 3V, VCM = V - to V+ VS = 2.5V to 10V, VCM = 0V VS = 2.5V to 10V, VCM = 0V No Load ISINK = 5mA ISINK = 25mA No Load ISOURCE = 5mA ISOURCE = 25mA VS = 5V VS = 3V VS = 5V, VSHDN = 0.3V VS = 3V, VSHDN = 0.3V VS = 5V, VSHDN = 0.3V VS = 3V, VSHDN = 0.3V VSHDN = 0.3V V+ VSHDN = 0.3V to 4.5V, RL = 100 VSHDN = 4.5V to 0.3V, RL = 100 Frequency = 6MHz VS = 5V, AV = -1, RL = 1k, VO = 4V VS = 5V, VOUT = 4VP-P VS = 5V, AV = 1, RL = 1k, VO = 2VP-P, fC = 5MHz 0.01%, VS = 5V, VSTEP = 2V, AV = 1, RL = 1k VS = 5V, AV = 2, RL = 150 VS = 5V, AV = 2, RL = 150 - 0.5 80 50 325 125 10 -78 60 0.015 0.05 35 30 75 9 60 79 74 73 68 V- 90 84 105 105 2.3 8 50 170 15 85 350 85 65 9 0.40 0.22 150 100 0.1 13 0.9 0.7 350 300 75 0.3 2.5 50 130 375 65 180 650 CONDITIONS VCM = V + VCM = V - + 0.2V VCM = V - + 0.2V to V + 0.1Hz to 10Hz f = 10kHz f = 10kHz MIN TYP 0.03 0.05 0.08 800 3.5 1.5 2 220 22 150 100 95 100 95 V+ MAX 0.6 1.5 2.1 UNITS A A A nVP-P nV/Hz pA/Hz pF V/mV V/mV V/mV dB dB dB dB V dB dB V mV mV mV mV mV mV mA mA mA mA mA A A A V V ns ns MHz V/s MHz dBc ns % Deg
CMRR
Common Mode Rejection Ratio CMRR Match (Channel-to-Channel) (Note 10) Input Common Mode Range
PSRR
Power Supply Rejection Ratio PSRR Match (Channel-to-Channel) (Note 10) Minimum Supply Voltage (Note 6)
VOL
Output Voltage Swing LOW (Note 7)
VOH
Output Voltage Swing HIGH (Note 7)
ISC IS
Short-Circuit Current Supply Current per Amplifier Disable Supply Current
ISHDN
SHDN Pin Current Shutdown Output Leakage Current
VL VH tON tOFF GBW SR FPBW HD tS G
SHDN Pin Input Voltage LOW SHDN Pin Input Voltage HIGH Turn-On Time Turn-Off Time Gain Bandwidth Product Slew Rate Full Power Bandwidth Harmonic Distortion Settling Time Differential Gain (NTSC) Differential Phase (NTSC)
3
LT1806/LT1807
ELECTRICAL CHARACTERISTICS
SYMBOL VOS PARAMETER Input Offset Voltage
The q denotes the specifications which apply over the 0C < TA < 70C temperature range. VS = 5V, 0V; VS = 3V, 0V; VSHDN = open; VCM = VOUT = half supply, unless otherwise noted.
CONDITIONS VCM = V + VCM = V - VCM = V + (LT1806 SOT-23) VCM = V - (LT1806 SOT-23) VCM = V + VCM = V - VCM = V - to V+ VCM = V - to V+ (LT1806 SOT-23)
q q q q q q q q q q q q q q q q
MIN
TYP 200 200 200 200 1.5 1.5 100 100 300 1 -5 6 0.03 0.05 0.03 0.05 0.08
MAX 700 700 850 850 5 5 700 850 1200 5 20 1.5 3.5 0.75 1.80 2.55
UNITS V V V V V/C V/C V V V A A A A A A A A V/mV V/mV V/mV dB dB dB dB
VOS TC VOS
Input Offset Voltage Drift (Note 8) Input Offset Voltage Shift
IB IB
Input Offset Voltage Match (Channel-to-Channel) VCM = V -, VCM = V + (Note 10) Input Bias Current VCM = V + - 0.2V VCM = V - + 0.4V Input Bias Current Shift Input Bias Current Match (Channel-to-Channel) (Note 10) VCM = V - + 0.4V to V + - 0.2V VCM = V + - 0.2V VCM = V - + 0.4V VCM = V + - 0.2V VCM = V - + 0.4V VCM = V - + 0.4V to
-15
IOS IOS AVOL
Input Offset Current Input Offset Current Shift Large-Signal Voltage Gain
V + - 0.2V
q q q q q q q q q q q q q q q q q q q q q q q q q q q q V + - 0.5
VS = 5V, VO = 0.5V to 4.5V, RL = 1k to VS/2 VS = 5V, VO = 1V to 4V, RL = 100 to VS/2 VS = 3V, VO = 0.5V to 2.5V, RL = 1k to VS/2 VS = 5V, VCM = V - to V + VS = 3V, VCM = V - to V+ VS = 5V, VCM = V - to V + VS = 3V, VCM = V - to V+ VS = 2.5V to 10V, VCM = 0V VS = 2.5V to 10V, VCM = 0V VCM = VO = 0.5V No Load ISINK = 5mA ISINK = 25mA No Load ISOURCE = 5mA ISOURCE = 25mA VS = 5V VS = 3V VS = 5V, VSHDN = 0.3V VS = 3V, VSHDN = 0.3V VS = 5V, VSHDN = 0.3V VS = 3V, VSHDN = 0.3V VSHDN = 0.3V
60 7.5 45 77 72 71 66 V- 88 82
175 20 140 94 89 94 89 V+ 105 105 2.3 12 60 180 30 110 360 2.5 60 140 425 120 220 700
CMRR
Common Mode Rejection Ratio CMRR Match (Channel-to-Channel) (Note 10) Input Common Mode Range
V dB dB V mV mV mV mV mV mV mA mA
PSRR
Power Supply Rejection Ratio PSRR Match (Channel-to-Channel) (Note 10) Minimum Supply Voltage (Note 6)
VOL
Output Voltage Swing LOW (Note 7)
VOH
Output Voltage Swing HIGH (Note 7)
ISC IS
Short-Circuit Current Supply Current per Amplifier Disable Supply Current
30 25
65 55 10 0.40 0.22 160 110 1 0.3 80 50 300 100 8 14 1.1 0.9 400 350
mA mA mA A A A V V ns ns MHz V/s MHz
ISHDN
SHDN Pin Current Shutdown Output Leakage Current SHDN Pin Input Voltage LOW SHDN Pin Input Voltage HIGH Turn-On Time Turn-Off Time Gain Bandwidth Product Slew Rate Full Power Bandwidth
VL VH tON tOFF GBW SR FPBW
VSHDN = 0.3V to 4.5V, RL = 100 VSHDN = 4.5V to 0.3V, RL = 100 Frequency = 6MHz VS = 5V, AV = -1, RL= 1k, VO = 4V VS = 5V, VO = 4VP-P
q q q q q
4
LT1806/LT1807
ELECTRICAL CHARACTERISTICS
SYMBOL VOS PARAMETER Input Offset Voltage
The q denotes the specifications which apply over the - 40C < TA < 85C temperature range. VS = 5V, 0V; VS = 3V, 0V; VSHDN = open; VCM = VOUT = half supply, unless otherwise noted. (Note 5)
CONDITIONS VCM = V + VCM = V - VCM = V + (LT1806 SOT-23) VCM = V - (LT1806 SOT-23) VCM = V + VCM = V - VCM = V - VCM = V - to V + (LT1806 SOT-23) VCM = V +, VCM = V - VCM = V + - 0.2V VCM = V - + 0.4V VCM = V - + 0.4V to V+ - 0.2V VCM = V + - 0.2V VCM = V - + 0.4V VCM = V + - 0.2V VCM = V - + 0.4V VCM = V - + 0.4V to V+ - 0.2V VS = 5V, VO = 0.5V to 4.5V, RL = 1k to VS/2 VS = 5V, VO = 1V to 4V, RL = 100 to VS/2 VS = 3V, VO = 0.5V to 2.5V, RL = 1k to VS/2 VS = 5V, VCM = V - to V + VS = 3V, VCM = V - to V+ VS = 5V, VCM = V - to V + VS = 3V, VCM = V - to V+ VS = 2.5V to 10V, VCM = 0V VS = 2.5V to 10V, VCM = 0V VCM = VO = 0.5V No Load ISINK = 5mA ISINK = 20mA No Load ISOURCE = 5mA ISOURCE = 20mA VS = 5V VS = 3V VS = 5V, VSHDN = 0.3.V VS = 3V, VSHDN = 0.3V VS = 5V, VSHDN = 0.3V VS = 3V, VSHDN = 0.3V VSHDN = 0.3V MIN
q q q q q q q q q q q q q q q q q q q q q q q q q q q q q q q q q q q q q q q q q q q q V + - 0.5
VOS TC VOS
Input Offset Voltage Drift (Note 8) Input Offset Voltage Shift Input Offset Voltage Match (Channel-to-Channel) (Note 10) Input Bias Current Input Bias Current Shift Input Bias Current Match (Channel-to-Channel) (Note 10) Input Offset Current Input Offset Current Shift Large-Signal Voltage Gain
TYP 200 200 200 200 1.5 1.5 100 100 200 1 -5 6 0.02 0.05 0.02 0.05 0.07 140 16 100 94 89 94 89 105 105 2.3 15 65 170 30 110 350 45 40 11 0.4 0.3 170 120 1.2
MAX 800 800 950 950 5 5 800 950 1400 6 22 1.8 4.0 0.9 2.1 3
UNITS V V V V V/C V/C V V V A A A A A A A A V/mV V/mV V/mV dB dB dB dB V dB dB V mV mV mV mV mV mV mA mA mA mA mA A A A V V ns ns MHz V/V MHz
IB IB
-16
IOS IOS AVOL
CMRR
Common Mode Rejection Ratio CMRR Match (Channel-to-Channel) (Note 10) Input Common Mode Range Power Supply Rejection Ratio PSRR Match (Channel-to-Channel) (Note 10) Minimum Supply Voltage (Note 6) Output Voltage Swing LOW (Note 7)
PSRR
50 6 35 75 71 69 65 V- 86 80
V+
VOL
VOH
Output Voltage Swing HIGH (Note 7)
2.5 70 150 400 130 240 700
ISC IS
Short-Circuit Current Supply Current per Amplifier Disable Supply Current SHDN Pin Current Shutdown Output Leakage Current SHDN Pin Input Voltage LOW SHDN Pin Input Voltage HIGH Turn-On Time Turn-Off Time Gain Bandwidth Product Slew Rate Full Power Bandwidth
22 20
ISHDN
16 1.2 1.0 450 400 0.3
VL VH tON tOFF GBW SR FPBW
VSHDN = 0.3V to 4.5V, RL = 100 VSHDN = 4.5V to 0.3V, RL = 100 Frequency = 6MHz VS= 5V, AV = -1, RL= 1k, VO = 4V VS = 5V, VO = 4VP-P
q q q q q
80 50 250 80 6
5
LT1806/LT1807
ELECTRICAL CHARACTERISTICS
SYMBOL PARAMETER VOS Input Offset Voltage
TA = 25C. VS = 5V, VSHDN = open; VCM = 0V, VOUT = 0V, unless otherwise noted.
CONDITIONS VCM = V + VCM = V - VCM = V + (LT1806 SOT-23) VCM = V - (LT1806 SOT-23) Input Offset Voltage Shift VCM = V - to V + VCM = V - to V + (LT1806 SOT-23) Input Offset Voltage Match (Channel-to-Channel) VCM = V -, VCM = V + (Note 10) Input Bias Current VCM = V + VCM = V - + 0.2V Input Bias Current Shift VCM = V - + 0.2V to V + Input Bias Current Match (Channel-to-Channel) VCM = V + (Note 10) VCM = V - + 0.2V Input Offset Current VCM = V + VCM = V - + 0.2V Input Offset Current Shift VCM = V - + 0.2V to V+ Input Noise Voltage 0.1Hz to 10Hz Input Noise Voltage Density f = 10kHz Input Noise Current Density f = 10kHz Input Capacitance f = 100kHz Large-Signal Voltage Gain VO = -4V to 4V, RL = 1k VO = -2.5V to 2.5V, RL = 100 Common Mode Rejection Ratio VCM = V - to V + CMRR Match (Channel-to-Channel) (Note 10) VCM = V - to V + Input Common Mode Range Power Supply Rejection Ratio V+ = 2.5V to 10V, V - = 0V PSRR Match (Channel-to-Channel) (Note 10) V+ = 2.5V to 10V, V - = 0V Output Voltage Swing LOW (Note 7) No Load ISINK = 5mA ISINK = 25mA Output Voltage Swing HIGH (Note 7) No Load ISOURCE = 5mA ISOURCE = 25mA Short-Circuit Current Supply Current per Amplifier Disable Supply Current VSHDN = 0.3V SHDN Pin Current VSHDN = 0.3V Shutdown Output Leakage Current VSHDN = 0.3V SHDN Pin Input Voltage LOW SHDN Pin Input Voltage HIGH Turn-On Time VSHDN = 0.3V to 4.5V, RL = 100 Turn-Off Time VSHDN = 4.5V to 0.3V, RL = 100 Gain Bandwidth Product Frequency = 6MHz Slew Rate AV = -1, RL = 1k, VO = 4V, Measured at VO = 3V Full Power Bandwidth VO = 8VP-P Harmonic Distortion AV = 1, RL = 1k, VO = 2VP-P, fC = 5MHz Settling Time 0.01%, VSTEP = 8V, AV = 1, RL = 1k Differential Gain (NTSC) AV = 2, RL = 150 Differential Phase (NTSC) AV = 2, RL = 150 MIN TYP 100 100 100 100 50 50 200 1 -5 6 0.03 0.05 0.03 0.04 0.07 800 3.5 1.5 2 300 27 106 106 105 105 14 55 180 20 90 360 85 11 0.4 150 0.3 MAX 700 700 750 750 700 750 1200 5 19 1.4 3.2 0.7 1.6 2.3 UNITS V V V V V V V A A A A A A A A nVP-P nV/Hz pA/Hz pF V/mV V/mV dB dB V dB dB mV mV mV mV mV mV mA mA mA A A V V ns ns MHz V/s MHz dBc ns % Deg
VOS
IB IB
-14
IOS IOS en in CIN AVOL CMRR
PSRR VOL
100 10 83 77 V- 90 84
V+
VOH
60 140 450 70 200 700 16 1.2 350 75 0.3
ISC IS ISHDN VL VH tON tOFF GBW SR FPBW HD tS G
40
V + - 0.5 80 50 325 140 5.5 -80 120 0.01 0.01
170 70
6
LT1806/LT1807
ELECTRICAL CHARACTERISTICS
SYMBOL VOS PARAMETER Input Offset Voltage
The q denotes specifications which apply over the 0C < TA < 70C temperature range. VS = 5V, VSHDN = open; VCM = 0V, VOUT = 0V, unless otherwise noted.
CONDITIONS VCM = V + VCM = V - VCM = V + (LT1806 SOT-23) VCM = V - (LT1806 SOT-23) VCM = V + VCM = V - VCM = V - to V + VCM = V - to V + (LT1806 SOT-23) VCM = V -, VCM = V + VCM = V + - 0.2V VCM = V - + 0.4V VCM = V - + 0.4V to V + - 0.2V VCM = V + - 0.2V VCM = V - + 0.4V VCM = V + - 0.2V VCM = V - + 0.4V VCM = V - + 0.4V to V + - 0.2V VO = -4V to 4V, RL = 1k VO = -2.5V to 2.5V, RL = 100 VCM = V - to V + VCM = V - to V +
q q q q q q q q q q q q q q q q q q q q q q
MIN
TYP 200 200 200 200 1.5 1.5 100 100 300 1 -6 7 0.03 0.04 0.03 0.04 0.07
MAX 800 800 900 900 5 5 800 900 1400 6 21 1.8 3.8 0.9 1.9 2.8
UNITS V V V V V/C V/C V V V A A A A A A A A V/mV V/mV dB dB
VOS TC VOS
Input Offset Voltage Drift (Note 8) Input Offset Voltage Shift Input Offset Voltage Match (Channel-to Channel) (Note 10)
IB IB
Input Bias Current Input Bias Current Shift Input Bias Current Match (Channel-to-Channel) (Note 10)
-15
IOS IOS AVOL CMRR
Input Offset Current Input Offset Current Shift Large-Signal Voltage Gain Common Mode Rejection Ratio CMRR Match (Channel-to-Channel) (Note 10) Input Common Mode Range
80 8 81 75 V- 88 82
250 25 100 100 V+ 105 106 18 60 185 40 110 360 80 160 500 140 240 750 20 1.4 400 0.3 80 50
V dB dB mV mV mV mV mV mV mA mA mA A A V V ns ns MHz V/s MHz
PSRR VOL
Power Supply Rejection Ratio PSRR Match (Channel-to-Channel) (Note 10) Output Voltage Swing LOW (Note 7)
V+ = 2.5V to 10V, V - = 0V V+ = 2.5V to 10V, V - = 0V No Load ISINK = 5mA ISINK = 25mA No Load ISOURCE = 5mA ISOURCE = 25mA
q q q q q q q q q q
VOH
Output Voltage Swing HIGH (Note 7)
ISC IS ISHDN VL VH tON tOFF GBW SR FPBW
Short-Circuit Current Supply Current per Amplifier Disable Supply Current SHDN Pin Current Shutdown Output Leakage Current SHDN Pin Input Voltage LOW SHDN Pin Input Voltage HIGH Turn-On Time Turn-Off Time Gain Bandwidth Product Slew Rate Full Power Bandwidth VSHDN = 0.3V to 4.5V, RL = 100 VSHDN = 4.5V to 0.3V, RL = 100 Frequency = 6MHz AV = -1, RL = 1k, VO = 4V, Measure at VO = 3V VO = 8VP-P VSHDN = 0.3V VSHDN = 0.3V VSHDN = 0.3V
35
75 14 0.4 160 1
q q q q q V + - 0.5 q q q q q
150 60
300 120 4.5
7
LT1806/LT1807
ELECTRICAL CHARACTERISTICS
SYMBOL VOS PARAMETER Input Offset Voltage
The q denotes the specifications which apply over the -40C < TA < 85C temperature range. VS = 5V, VSHDN = open; VCM = 0V, VOUT = 0V, unless otherwise noted. (Note 5)
CONDITIONS VCM = V + VCM = V - VCM = V + (LT1806 SOT-23) VCM = V - (LT1806 SOT-23) VCM = V + VCM = V - VCM = V - to V+ VCM = V - to V+ (LT1806 SOT-23) VCM = V - to V+ VCM = V + - 0.2V VCM = V - + 0.4V VCM = V - + 0.4V to V + - 0.2V VCM = V + - 0.2V VCM = V - + 0.4V VCM = V + - 0.2V VCM = V - + 0.4V VCM = V - + 0.4V to V + - 0.2V VO = -4V to 4V, RL = 1k VO = -2V to 2V, RL =100 VCM = V - to V + VCM = V- to V +
q q q q q q q q q q q q q q q q q q q q q q
MIN
TYP 200 200 200 200 1.5 1.5 100 100 300 1.2 -5 6 0.03 0.04 0.03 0.04 0.07
MAX 900 900 975 975 5 5 900 975 1600 7 23 2.0 4.5 1.0 2.2 3.2
UNITS V V V V V/C V/C V V V A A A A A A A A V/mV V/mV dB dB
VOS TC VOS
Input Offset Voltage Drift (Note 8) Input Offset Voltage Shift Input Offset Voltage Match (Channel-to-Channel) (Note 10)
IB IB
Input Bias Current Input Bias Current Shift Input Bias Current Match (Channel-to-Channel) (Note 10)
-16
IOS IOS AVOL CMRR
Input Offset Current Input Offset Current Shift Large-Signal Voltage Gain Common Mode Rejection Ratio CMRR Match (Channel-to-Channel) (Note 10) Input Common Mode Range
60 7 80 74 V- 86 80
175 17 100 100 V+ 105 105 20 65 200 50 115 360 100 170 500 160 260 700 22 1.5 450 0.3 80 50
V dB dB mV mV mV mV mV mV mA mA mA A A V V ns ns MHz V/s MHz
PSRR VOL
Power Supply Rejection Ratio PSRR Match (Channel-to-Channel) (Note 10) Output Voltage Swing LOW (Note 7)
V+ = 2.5V to 10V, V - = 0V No Load ISINK = 5mA ISINK = 20mA No Load ISOURCE = 5mA ISOURCE = 20mA
q q q q q q q q q q
VOH
Output Voltage Swing HIGH (Note 7)
ISC IS ISHDN VL VH tON tOFF GBW SR FPBW
Short-Circuit Current Supply Current Disable Supply Current SHDN Pin Current Shutdown Output Leakage Current SHDN Pin Input Voltage LOW SHDN Pin Input Voltage HIGH Turn-On Time Turn-Off Time Gain Bandwidth Product Slew Rate Full Power Bandwidth VSHDN = 0.3V to 4.5V, RL = 100 VSHDN = 4.5V to 0.3V, RL = 100 Frequency = 6MHz AV = -1, RL = 1k, VO = 4V, Measured at VO = 3V VO = 8VP-P VSHDN = 0.3V VSHDN = 0.3V VSHDN = 0.3V
25
55 15 0.45 170 1.2
q q q q q V + - 0.5 q q q q q
125 50
290 100 4
Note 1: Absolute maximum ratings are those values beyond which the life of the device may be impaired.
Note 2: The inputs are protected by back-to-back diodes. If the differential input voltage exceeds 1.4V, the input current should be limited to less than 10mA.
8
LT1806/LT1807
ELECTRICAL CHARACTERISTICS
Note 3: A heat sink may be required to keep the junction temperature below the absolute maximum rating when the output is shorted indefinitely. Note 4: The LT1806C/LT1806I and LT1807C/LT1807I are guaranteed functional over the temperature range of -40C and 85C. Note 5: The LT1806C/LT1807C are guaranteed to meet specified performance from 0C to 70C. The LT1806C/LT1807C are designed, characterized and expected to meet specified performance from -40C to 85C but are not tested or QA sampled at these temperatures. The LT1806I/LT1807I are guaranteed to meet specified performance from -40C to 85C. Note 6: Minimum supply voltage is guaranteed by power supply rejection ratio test. Note 7: Output voltage swings are measured between the output and power supply rails. Note 8: This parameter is not 100% tested. Note 9: Thermal resistance varies depending upon the amount of PC board metal attached to the V - pin of the device. JA is specified for a certain amount of 2oz copper metal trace connecting to the V - pin as described in the thermal resistance tables in the Applications Information section. Note 10: Matching parameters are the difference between the two amplifiers of the LT1807.
TYPICAL PERFOR A CE CHARACTERISTICS
VOS Distribution, VCM = 0V (PNP Stage)
50 VS = 5V, 0V VCM = 0V 50
40
PERCENT OF UNITS (%)
PERCENT OF UNITS (%)
30
30
PERCENT OF UNITS (%)
20
10
0 -500
-300 100 300 -100 INPUT OFFSET VOLTAGE (V)
Supply Current per Amp vs Supply Voltage
20 500 400
SUPPLY CURRENT (mA)
OFFSET VOLTAGE (V)
15 TA = 125C 10 TA = 25C 5 TA = -55C
200 100 0 -100 -200 -300 -400 VS = 5V, 0V TYPICAL PART TA = -55C TA = 25C
INPUT BIAS CURRENT (A)
0 0 1 2 3 4 5 6 7 8 9 10 11 12 TOTAL SUPPLY VOLTAGE (V)
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18067 G01
VOS Distribution, VCM = 5V (NPN Stage)
VS = 5V, 0V VCM = 5V 50
VOS Shift for VCM = 0V to 5V
VS = 5V, 0V
40
40
30
20
20
10
10
500
0 -500
-300 100 300 -100 INPUT OFFSET VOLTAGE (V)
500
18067 G02
0 -500
-300 100 300 -100 INPUT OFFSET VOLTAGE (V)
500
18067 G03
Offset Voltage vs Input Common Mode
5 TA = 125C 0
Input Bias Current vs Common Mode Voltage
VS = 5V, 0V TA = 125C TA = 25C TA = -55C
300
-5
TA = 125C TA = 25C TA = -55C -1 0 1 2 3 4 5 COMMON MODE VOLTAGE (V) 6
-500
-10 0 1 3 4 2 INPUT COMMON MODE VOLTAGE (V) 5
18067 G05
18067 G06
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LT1806/LT1807 TYPICAL PERFOR A CE CHARACTERISTICS
Input Bias Current vs Temperature
2
OUTPUT SATURATION VOLTAGE (V)
0
INPUT BIAS (A)
-1 -2 -3 -4 -5 -6 -7
NPN ACTIVE VS = 5V, 0V VCM = 5V
1
OUTPUT SATURATION VOLTAGE (V)
1
PNP ACTIVE VS = 5V, 0V VCM = 0V
-8 -50 -35 -20 - 5 10 25 40 55 TEMPERATURE (C)
Minimum Supply Voltage
1.0 120
OUTPUT SHORT-CIRCUIT CURRENT (mA)
CHANGE IN OFFSET VOLTAGE (mV)
0.8 0.6 0.4 0.2 0 -0.2 -0.4 -0.6 -0.8 -1.0 1.0 1.5 2.0 2.5 3.0 3.5 4.0 4.5 TOTAL SUPPLY VOLTAGE (V) 5.0 TA = 25C TA = -55C TA = 125C
60 40 20 0 -20 -40 -60
"SINKING"
SUPPLY CURRENT (mA)
SHDN Pin Current vs SHDN Pin Voltage
20 0 VS = 5V, 0V
SHDN PIN CURRENT (A)
-20
INPUT VOLTAGE (V)
-40 -60 -80 -100 -120 -140 -160 -180 0
200 100 0 -100 -200 -300 -400 -500
INPUT VOLTAGE (V)
TA = 125C
TA = 25C TA = -55C
1
3 4 2 SHDN PIN VOLTAGE (V)
10
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70
18067 G07
Output Saturation Voltage vs Load Current (Output Low)
10 VS = 5V 10
Output Saturation Voltage vs Load Current (Output High)
VS = 5V
1
0.1 TA = 125C 0.01 TA = -55C
0.1
TA = 125C TA = 25C
TA = 25C
0.01
TA = -55C
85
0.001 0.01
0.1 1 10 LOAD CURRENT (mA)
100
18067 G08
0.001 0.01
0.1 1 10 LOAD CURRENT (mA)
100
18067 G09
Output Short-Circuit Current vs Power Supply Voltage
18 TA = -55C TA = 25C TA = 125C 16 14 12 10 8 6 4 2 0 1.5 4.0 4.5 2.0 2.5 3.0 3.5 POWER SUPPLY VOLTAGE (V) 5.0 100 80
Supply Current vs SHDN Pin Voltage
VS = 5V, 0V
TA = 125C TA = 25C
"SOURCING" TA = -55C TA = 125C
TA = -55C
-80 TA = 25C
-100
0
1
4 3 2 SHDN PIN VOLTAGE (V)
18067 G12
5
18067 G10
18067 G11
Open-Loop Gain
500 400 300 RL = 1k VS = 3V, 0V RL TO GND 500 400 300 200 100 0 -100 -200 -300 -400 -500 0 0.5 1.5 2.0 1.0 OUTPUT VOLTAGE (V) 2.5 3.0
Open-Loop Gain
VS = 5V, 0V RL TO GND
RL = 1k
RL = 100
RL = 100
5
18067 G13
0 0.5 1.0 1.5 2.0 2.5 3.0 3.5 4.0 4.5 5.0 OUTPUT VOLTAGE (V)
18067 G15
18067 G14
LT1806/LT1807 TYPICAL PERFOR A CE CHARACTERISTICS
Open-Loop Gain
500 400 300 200 100 0 -100 -200 -300 -400 -500 -5 -4 -3 -2 -1 0 1 2 3 OUTPUT VOLTAGE (V) 4 5 RL = 100 RL = 1k OFFSET VOLTAGE (mV) VS = 5V 2.5 2.0 1.5 1.0 0.5 0 -0.5 -1.0 -1.5 -2.0 -2.5 -100 -80 -60 -40 -20 0 20 40 60 80 100 OUTPUT CURRENT (mA)
18067 G17
OFFSET VOLTAGE DRIFT (V)
INPUT VOLTAGE (V)
Input Noise Voltage vs Frequency
12 10 NOISE CURRENT (pA/Hz) NOISE VOLTAGE (nV/Hz) 8 6 4 2 0 0.1 1 10 FREQUENCY (kHz) 100
18067 G19
VS = 5V, 0V
OUTPUT VOLTAGE (nV)
NPN ACTIVE VCM = 4.5V
PNP ACTIVE VCM = 2.5V
Gain Bandwidth and Phase Margin vs Supply Voltage
TA = 25C PHASE MARGIN GAIN BANDWIDTH (MHz) 55 50 45
GAIN BANDWIDTH (MHz)
SLEW RATE (V/s)
400 350 300 250 200 0 1 2345678 TOTAL SUPPLY VOLTAGE (V) 9 10 GAIN BANDWIDTH PRODUCT
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18067 G16 18067 G22
Offset Voltage vs Output Current
VS = 5V TA = 125C TA = 25C
Warm-Up Drift vs Time (LT1806S8)
45 40 35 30 25 20 15 10 5 0 0 20 40 60 80 100 120 140 160 TIME AFTER POWER-UP (SEC)
18067 G18
VS = 5V
TA = -55C
VS = 2.5V VS = 1.5V
Input Noise Current vs Frequency
12 10 8 6 4 2 0 PNP ACTIVE VCM = 2.5V VS = 5V, 0V
1000 800 600 400 200 0 -200 -400 -600
0.1Hz to 10Hz Output Voltage Noise
NPN ACTIVE VCM = 4.5V 0.1 1 10 FREQUENCY (kHz) 100
18067 G19
-800 -1000 0 1 2 3 456 TIME (SEC) 7 8 9 10
18067 G21
Gain Bandwidth and Phase Margin vs Temperature
55 50 PHASE MARGIN VS = 5V PHASE MARGIN VS = 3V 45
Slew Rate vs Temperature
175 AV = -1 RF = RG = 1k RL = 1k VS = 5V 125 VS = 2.5V 100
40 35 30
150
PHASE MARGIN (DEG)
PHASE MARGIN (DEG)
40 35 30
400 350 300 250 200 -55 -35 -15
GBW PRODUCT VS = 5V GBW PRODUCT VS = 3V
5 25 45 65 85 105 125 TEMPERATURE (C)
18067 G23
75 -55 -35 -15
5 25 45 65 85 105 125 TEMPERATURE (C)
18067 G24
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LT1806/LT1807 TYPICAL PERFOR A CE CHARACTERISTICS
Gain and Phase vs Frequency
70 60 50 40 PHASE VS = 5V PHASE VS = 3V 225 180 135 90
GAIN (dB)
GAIN (dB)
GAIN (dB)
30 20 10 0 -10 -20 CL = 5pF RL = 100 -30 1 0.1 GAIN VS = 5V GAIN VS = 3V 100
10 FREQUENCY (MHz)
Output Impedance vs Frequency
600 100 OUTPUT IMPEDANCE () 10 1 0.1 0.01 0.001 100k 100
90 80 70 60 50 40 30 20 10 0 0.01 0.1 1 10 FREQUENCY (MHz)
POWER SUPPLY REJECTION RATIO (dB)
COMMON MODE REJECTION RATIO (dB)
VS = 5V, 0V
AV = 2 AV = 10 AV = 1
1M
10M FREQUENCY (Hz)
Series Output Resistor vs Capacitive Load
50 VS = 5V, 0V 45 AV = 1 40
OVERSHOOT (%)
50
OVERSHOOT (%)
35 30 25 20 15 10 5 0 10
ROS = 10 ROS = 20
ROS = RL = 50
100 CAPACITIVE LOAD (pF)
12
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18067 G25
Gain vs Frequency (AV = 1)
30 CL = 10pF 24 RL = 100 18 12
PHASE (DEG)
Gain vs Frequency (AV = 2)
21 CL = 10pF 18 RL = 100 15 12 9 6 3 0 -3 -6 VS = 3V VS = 5V
45 0 -45 -90
6 0 -6 -12 -18 -24 -36 0.1 1 10 FREQUENCY (MHz) 100 500
18067 G26
VS = 5V VS = 3V
-135 -180 -225 500
-9 0.1
1
10 FREQUENCY (MHz)
100
500
18067 G27
Common Mode Rejection Ratio vs Frequency
VS = 5V, 0V 100 90 80 70 60 50 40 30 20 10
Power Supply Rejection Ratio vs Frequency
VS = 5V, 0V TA = 25C
POSITIVE SUPPLY
NEGATIVE SUPPLY
100M
500M
100
500
0 0.001
0.01
0.1 1 FREQUENCY (MHz)
10
100
18067 G30
18067 G28
18067 G29
Series Output Resistor vs Capacitive Load
VS = 5V, 0V 45 AV = 2 40 35 30 25 20 15 10 5 0 ROS = 20 ROS = 10
0.01% Settling Time
INPUT SIGNAL GENERATION (2V/DIV) OUTPUT SETTLING RESOLUTION (2mV/DIV)
ROS = RL = 50
1000
18067 G31
10
100 CAPACITIVE LOAD (pF)
1000
18067 G32
VS = 5V 20ns/DIV VOUT = 4V RL = 500 tS = 120ns (SETTLING TIME)
18067 G33
LT1806/LT1807 TYPICAL PERFOR A CE CHARACTERISTICS
Distortion vs Frequency
-40 -50 AV = 1 VOUT = 2VP-P VS = 5V -40 -50
DISTORTION (dBc)
DISTORTION (dBc)
RL = 100, 3RD RL = 100, 2ND
DISTORTION (dBc)
-60 -70 RL = 100, 2ND -80 -90 -100 -110 0.3 RL = 100, 3RD RL = 1k, 3RD RL = 1k, 2ND
1 FREQUENCY (MHz)
10
Distortion vs Frequency
-40 -50 -60 AV = 2 VOUT = 2VP-P VS = 5V, 0V RL = 100, 3RD RL = 100, 2ND -70 -80 RL = 1k, 3RD -90 -100 -110 -120 0.3 1 FREQUENCY (MHz)
18067 G37
OUTPUT VOLTAGE SWING (VP-P)
DISTORTION (dBc)
5V Large-Signal Response
0V
VS = 5V FREQ = 1.92MHz AV = 1 RL = 1k
40ns/DIV
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18067 G34
Distortion vs Frequency
AV = 1 VOUT = 2VP-P VS = 5V, 0V -40 -50 -60 -70 -80 -90 -100 -110
Distortion vs Frequency
AV = 2 VOUT = 2VP-P VS = 5V RL = 100, 3RD RL = 100, 2ND RL = 1k, 2ND
-60 -70 -80
RL = 1k, 2ND -90 RL = 1k, 3RD -100 -110 0.3
RL = 1k, 3RD
30
1 FREQUENCY (MHz)
10
30
18067 G35
-120 0.3
1 FREQUENCY (MHz)
10
30
18067 G36
Maximum Undistorted Output Signal vs Frequency
4.6 4.5 4.4 4.3 4.2 4.1 4.0 3.9 0.1 VS = 5V, 0V AV = -1
RL = 1k, 2ND
AV = +2
10
30
1 10 FREQUENCY (MHz)
100
18067 G38
5V Small-Signal Response
5V Large-Signal Response
0V 0.5V
18067 G39
VS = 5V FREQ = 4.48MHz AV = 1 RL = 1k
20ns/DIV
18067 G40
VS = 5V, 0V FREQ = 5.29MHz AV = 1 RL = 1k
20ns/DIV
18067 G41
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LT1806/LT1807 TYPICAL PERFOR A CE CHARACTERISTICS
5V Small-Signal Response Output Overdriven Recovery Shutdown Response
0V
VS = 5V, 0V AV = 1 RL = 1k
10ns/DIV
APPLICATIO S I FOR ATIO
Rail-to-Rail Characteristics
The LT1806/LT1807 have input and output signal range that covers from negative power supply to positive power supply. Figure 1 depicts a simplified schematic of the amplifier. The input stage is comprised of two differential amplifiers, a PNP stage Q1/Q2 and a NPN stage Q3/Q4 that are active over different ranges of common mode input voltage. The PNP differential pair is active between the negative supply to approximately 1.5V below the positive
V+ R6 40k V+ ESDD5 D9 SHDN ESDD6 V- D5 -IN ESDD4 V- V+ ESDD3 D7 Q4 Q3 R7 100k
Q16
Q17 V+ ESDD1 +IN
V- ESDD2 D1
D6
D8
BIAS GENERATION
V-
Figure 1. LT1806 Simplified Schematic Diagram
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18067 G42
VIN (1V/DIV) 0V VOUT (2V/DIV) 0V
VSHDN (2V/DIV) 0V VOUT (2V/DIV) 0V VS = 5V, 0V AV = 2 RL = 1k 100ns/DIV VS = 5V, 0V AV = 2 RL = 100 200ns/DIV
18067 G43
18067 G44
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supply. As the input voltage moves closer toward the positive supply, the transistor Q5 will steer the tail current I1 to the current mirror Q6/Q7, activating the NPN differential pair. The PNP pair becomes inactive for the rest of the input common mode range up to the positive supply. A pair of complementary common emitter stages Q14/ Q15 that enable the output to swing from rail to rail constructs the output stage. The capacitors C1 and C2 form the local feedback loops that lower the output
R3
R4
R5
+
I1
Q11
Q12
Q13 C2
Q15
D2
Q5
VBIAS CC Q1 Q2 D3 Q10 D4 Q9 Q8
+
I2 OUT V-
BUFFER AND OUTPUT BIAS
C1 Q7 Q6 R1 R2
18067 F01
Q14
LT1806/LT1807
APPLICATIO S I FOR ATIO
impedance at high frequency. These devices are fabricated on Linear Technology's proprietary high speed complementary bipolar process. Power Dissipation The LT1806/LT1807 amplifiers combine high speed with large output current in a small package, so there is a need to ensure that the die's junction temperature does not exceed 150C. The LT1806 is housed in an SO-8 package or a 6-lead SOT-23 package and the LT1807 is in an SO-8 or 8-lead MSOP package. All packages have the V - supply pin fused to the lead frame to enhance the thermal conductance when connecting to a ground plane or a large metal trace. Metal trace and plated through-holes can be used to spread the heat generated by the device to the backside of the PC board. For example, on a 3/32" FR-4 board with 2oz copper, a total of 660 square millimeters connects to Pin 4 of LT1807 in an SO-8 package (330 square millimeters on each side of the PC board) will bring the thermal resistance, JA, to about 85C/W. Without extra metal trace beside the power line connecting to the V - pin to provide a heat sink, the thermal resistance will be around 105C/W. More information on thermal resistance for all packages with various metal areas connecting to the V - pin is provided in Tables 1, 2 and 3.
Table 1. LT1806 6-Lead SOT-23 Package
COPPER AREA TOPSIDE (mm2) 270 100 20 0 BOARD AREA (mm2) 2500 2500 2500 2500 THERMAL RESISTANCE (JUNCTION-TO-AMBIENT) 135C/W 145C/W 160C/W 200C/W
Device is mounted on topside.
Table 2. LT1806/LT1807 SO-8 Package
COPPER AREA TOPSIDE BACKSIDE (mm2) (mm2) 1100 330 35 35 0 1100 330 35 0 0 BOARD AREA (mm2) 2500 2500 2500 2500 2500 THERMAL RESISTANCE (JUNCTION-TO-AMBIENT) 65C/W 85C/W 95C/W 100C/W 105C/W
Device is mounted on topside.
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Table 3. LT1807 8-Lead MSOP Package
COPPER AREA TOPSIDE BACKSIDE (mm2) (mm2) 540 100 100 30 0 540 100 0 0 0 BOARD AREA THERMAL RESISTANCE (mm2) (JUNCTION-TO-AMBIENT) 2500 2500 2500 2500 2500 110C/W 120C/W 130C/W 135C/W 140C/W Device is mounted on topside.
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Junction temperature TJ is calculated from the ambient temperature TA and power dissipation PD as follows: TJ = TA + (PD * JA) The power dissipation in the IC is the function of the supply voltage, output voltage and the load resistance. For a given supply voltage, the worst-case power dissipation PD(MAX) occurs at the maximum quiescent supply current and at the output voltage which is half of either supply voltage (or the maximum swing if it is less than 1/2 the supply voltage). PD(MAX) is given by: PD(MAX) = (VS * IS(MAX)) + (VS/2)2/RL Example: An LT1807 in SO-8 mounted on a 2500mm 2 area of PC board without any extra heat spreading plane connected to its V - pin has a thermal resistance of 105C/W, JA. Operating on 5V supplies with both amplifiers simultaneously driving 50 loads, the worstcase power dissipation is given by: PD(MAX) = 2 * (10 * 14mA) + 2 * (2.5)2/50 = 0.28 + 0.25 = 0.53W The maximum ambient temperature that the part is allowed to operate is: TA = TJ - (PD(MAX) * 105C/W) = 150C - (0.53W * 105C/W) = 94C To operate the device at higher ambient temperature, connect more metal area to the V - pin to reduce the thermal resistance of the package as indicated in Table 2.
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LT1806/LT1807
APPLICATIO S I FOR ATIO
Input Offset Voltage
The offset voltage will change depending upon which input stage is active and the maximum offset voltage is guaranteed to less than 550V. To maintain the precision characteristics of the amplifier, the change of VOS over the entire input common mode range (CMRR) is limited to be less than 550V on a single 5V and 3V supply. Input Bias Current The input bias current polarity depends on a given input common voltage at which the input stage is operating. When the PNP input stage is active, the input bias currents flow out of the input pins. When the NPN input stage is activated, the input bias current flows into the input pins. Because the input offset current is less than the input bias current, matching the source resistances at the input pins will reduce total offset error. Output The LT1806/LT1807 can deliver a large output current, so the short-circuit current limit is set around 90mA to prevent damage to the device. Attention must be paid to keep the junction temperature of the IC below the absolute maximum rating of 150C (refer to the Power Dissipation section) when the output is continuously short-circuited. The output of the amplifier has reverse-biased diodes connected to each supply. If the output is forced beyond either supply, unlimited current will flow through these diodes. If the current is transient and limited to one hundred milliamps or less, no damage to the device will occur. Overdrive Protection When the input voltage exceeds the power supplies, two pairs of crossing diodes D1 to D4 will prevent the output from reversing polarity. If the input voltage exceeds either power supply by 700mV, diode D1/D2 or D3/D4 will turn on to keep the output at the proper polarity. For the phase reversal protection to perform properly, the input current must be limited to less than 5mA. If the amplifier is
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severely overdriven, an external resistor should be used to limit the overdrive current. The LT1806/LT1807's input stages are also protected against large differential input voltages of 1.4V or higher by a pair of back-to-back diodes, D5/D8, that prevent the emitter-base breakdown of the input transistors. The current in these diodes should be limited to less than 10mA when they are active. The worst-case differential input voltage usually occurs when the input is driven while the output is shorted to ground in a unity gain configuration. In addition, the amplifier is protected against ESD strikes up to 3kV on all pins by a pair of protection diodes, ESDD1 to ESDD6, on each pin that are connected to the power supplies as shown in Figure 1. Capacitive Load The LT1806/LT1807 are optimized for high bandwidth and low distortion applications. They can drive a capacitive load of about 20pF in a unity-gain configuration, and more for higher gain. When driving a larger capacitive load, a resistor of 10 to 50 should be connected between the output and the capacitive load to avoid ringing or oscillation. The feedback should still be taken from the output so that the resistor will isolate the capacitive load to ensure stability. Graphs on capacitive loads indicate the transient response of the amplifier when driving the capacitive load with a specified series resistor. Feedback Components When feedback resistors are used to set up gain, care must be taken to ensure that the pole formed by the feedback resistors and the total capacitance at the inverting input does not degrade stability. For instance, the LT1806/ LT1807 in a noninverting gain of 2, set up with two 1k resistors and a capacitance of 3pF (part plus PC board) will probably ring in transient response. The pole is formed at 106MHz that will reduce phase margin by 34 degrees when the crossover frequency of the amplifier is around 70MHz. A capacitor of 3pF or higher connected across the feedback resistor will eliminate any ringing or oscillation.
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LT1806/LT1807
APPLICATIO S I FOR ATIO
SHDN Pin
The LT1806 has a SHDN pin to reduce the supply current to less than 0.9mA. When the SHDN pin is pulled low, it will generate a signal to power down the device. If the pin is left unconnected, an internal pull-up resistor of 40k will keep the part fully operating as shown in Figure 1. The output
TYPICAL APPLICATIO S
Driving A/D Converter The LT1806/LT1807 have 60ns settling time to 0.01% on a 2V step signal, and 20 output impedance at 100MHz, that makes them ideal for driving high speed A/D converters. With the rail-to-rail input and output, and low supply voltage operation, the LT1806/LT1807 are also desirable for single supply applications. As shown in the application on the front page of this data sheet, the LT1807 drives a 10Msps, 12-bit, LTC1420 ADC in a gain of 20. Driving the LTC1420 differentially will optimize the signal-to-noise ratio, SNR, and the total harmonic distortion, THD, of the A/D converter. The lowpass filter, R5, R6 and C3 reduce noise or distortion products that might come from the input signal. High quality capacitors and resistors, NPO chip capacitor and metal film surface mount resistors, should be used since these components can add to distortion. The voltage glitch of the converter, due to its sampling nature is buffered by the LT1807, and the ability of the amplifier to settle it quickly will affect the spurious free dynamic range of the system. Figure 2 depicts the LT1806 driving LTC1420 at noninverting gain of 2 configuration. The FFT responses show a better than 92dB of spurious free dynamic range, SFDR.
5V 5V VIN 1.5VP-P
+
LT1806
R3 49.9 +AIN C1 470pF -5V R2 1k -AIN
AMPLITUDE (dB)
-
LTC1420 PGA GAIN = 1 REF = 2.048V
-5V R1 1k
Figure 2. Noninverting A/D Driver
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will be high impedance during shutdown, and the turn-on and turn-off time is less than 100ns. Because the input is protected by a pair of back to back diodes, the input signal will feed through to the output during shutdown mode if the amplitude of signal between the inputs is larger than 1.4V.
0 -20 -40 -60 -80 VS = 5V AV = 2 fSAMPLE = 10Msps fIN = 1.4086MHz SFDR = 92.5dB
* * * 12 BITS 10Msps
18067 F02
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-100 -120 0 1 2 3 FREQUENCY (MHz) 4 5
18067 F03
Figure 3. 4096 Point FFT Response
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LT1806/LT1807
TYPICAL APPLICATIO S
Single Supply Video Line Driver The LT1806/LT1807 are wideband rail-to-rail op amps with large output current that allows them to drive video signals in low supply applications. Figure 4 depicts a single supply video line driver with AC coupling to minimize the quiescent power dissipation. Resistors R1 and R2 are used to level-shift the input and output to provide the largest signal swing. The gain of 2 is set up with R3 and R4 to restore the signal at VOUT, which is attenuated by 6dB due to the matching of the 75 line with the back-terminated resistor, R5. The back termination will eliminate any reflection of the signal that comes from the load. The input termination resistor, RT, is optional--it is used only if matching of the incoming line is necessary. The values of C1, C2 and C3 are selected to minimize the droop of the luminance signal. In some less stringent requirements, the value of capacitors could be reduced. The - 3dB bandwidth of the driver is about 90MHz on 5V supply, and the amount of peaking will vary upon the value of capacitor C4.
C1 33F
VIN RT 75
2
+
VOLTAGE GAIN (dB)
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5V R1 5k R2 5k
3
+ -
7 LT1806 4 R4 1k C4 3pF 6
C3 1000F
R5 75
75 COAX CABLE VOUT RLOAD 75
18067 F04
+
R3 1k
+
C2 150F
Figure 4. 5V Single Supply Video Line Driver
5 4 3 2 1 0 -1 -2 -3 -4
VS = 5V, 0V
-5 0.2
1
10 FREQUENCY (MHz)
100
18067 F05
Figure 5. Video Line Driver Frequency Response
LT1806/LT1807
TYPICAL APPLICATIO S
Single 3V Supply, 4MHz, 4th Order Butterworth Filter Benefiting from a low voltage supply operation, low distortion and rail-to-rail output of LT1806/LT1807, a low distortion filter that is suitable for antialiasing can be built as shown in Figure 6. On a 3V supply, the filter built with LT1807 has a passband of 4MHz with 2.5VP-P signal and stopband that is greater than 70dB to frequency of 100MHz. As an option to minimize the DC offset voltage at the output, connect a series resistor of 365 and a bypass capacitor at the noninverting inputs of the amplifiers as shown in Figure 6.
232 VIN
VS 2
365 (OPTIONAL)
Figure 6. Single 3V Supply, 4MHz, 4th Order Butterworth Filter
GAIN (dB)
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232 47pF 274 22pF 665 220pF
-
1/2 LT1807
274
562 470pF
-
1/2 LT1807 VOUT
+
4.7F (OPTIONAL)
+
18067 F06
10 0 -10 -20 -30 -40 -50 -60 -70 -80 VS = 3V, 0V VIN = 2.5VP-P 100k 1M 10M FREQUENCY (Hz) 100M
18067 F07
-90 10k
Figure 7. Filter Frequency Response
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LT1806/LT1807
TYPICAL APPLICATIO S
1MHz Series Resonant Crystal Oscillator with Square and Sinusoid Outputs Figure 8 shows a classic 1MHz series resonant crystal oscillator. At series resonance, the crystal is a low impedance and the positive feedback connection is what brings about oscillation at the series resonance frequency. The RC feedback around the other path ensures that the circuit does not find a stable DC operating point and refuse to oscillate. The comparator output is a 1MHz square wave with a measured jitter of 28psRMS with a 5V supply and 40psRMS with a 3V supply. On the other side of the crystal, however, is an excellent looking sine wave except for the fact of the small high frequency glitch caused by the fast edge and the crystal capacitance (middle trace of Figure 9). Sinusoid amplitude stability is maintained by the fact that the sine wave is basically a filtered version of the square wave; the usual amplitude control loops associated with sinusoidal oscillators are not immediately necessary.1 One can make use of this sine wave by buffering and filtering it, and this is the combined task of the LT1806. It is configured as a bandpass filter with a Q of 5 and does a good job of cleaning up and buffering the sine wave. Distortion was measured at -70dBc and - 60dBc on the second and third harmonics.
1Amplitude will be a linear function of comparator output swing, which is supply dependent and therefore controllable. The important difference here is that any added amplitude stabilization loop will not be faced with the classical task of avoiding regions of nonoscillation versus clipping.
1MHZ AT-CUT VS R1 1k R2 1k VS 2 1 LT1713 3
R4 210
+ -
6
7 8 4 SQUARE WAVE
LE 5
C1 0.1F
Figure 8. LT1713 Comparator is Configured as a Series Resonant Crystal Oscillator. The LT1806 Op Amp is Configured in a Q = 5 Bandpass Filter with fC = 1MHz
Figure 9. Oscillator Waveforms with VS = 3V. Top Trace is Comparator Output. Middle Trace is Crystal Feedback to Pin 2 at LT1713. Bottom Trace is Buffered, Inverted and Bandpass Filtered with a Q of 5 by the LT1806
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1k
R5 6.49k 100pF R6 162 C3 100pF R9 2k VS C2 0.1F
C4 100pF R7 15.8k VS 2
- +
4
7 LT1806 6 1 (NC) SINE WAVE
3 R8 2k
18067 F08
R3 1k
VS = 2.7V TO 6V
3V/DIV
1V/DIV
1V/DIV
200ns/DIV
1806 F09
LT1806/LT1807
PACKAGE DESCRIPTIO
SOT-23 (Original) A A1 A2 L .90 - 1.45 (.035 - .057) .00 - 0.15 (.00 - .006) .90 - 1.30 (.035 - .051) .35 - .55 (.014 - .021)
SOT-23 (ThinSOT) 1.00 MAX (.039 MAX) .01 - .10 (.0004 - .004) .80 - .90 (.031 - .035) .30 - .50 REF (.012 - .019 REF) 2.60 - 3.00 (.102 - .118) 1.50 - 1.75 (.059 - .069) (NOTE 3) PIN ONE ID
.20 (.008) DATUM `A' A A2
L NOTE: 1. CONTROLLING DIMENSION: MILLIMETERS MILLIMETERS 2. DIMENSIONS ARE IN (INCHES)
3. DRAWING NOT TO SCALE 4. DIMENSIONS ARE INCLUSIVE OF PLATING 5. DIMENSIONS ARE EXCLUSIVE OF MOLD FLASH AND METAL BURR 6. MOLD FLASH SHALL NOT EXCEED .254mm 7. PACKAGE EIAJ REFERENCE IS: SC-74A (EIAJ) FOR ORIGINAL JEDEC MO-193 FOR THIN
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Dimensions in inches (millimeters) unless otherwise noted.
S6 Package 6-Lead Plastic SOT-23
(Reference LTC DWG # 05-08-1634) (Reference LTC DWG # 05-08-1636)
2.80 - 3.10 (.110 - .118) (NOTE 3)
.95 (.037) REF
.25 - .50 (.010 - .020) (6PLCS, NOTE 2)
.09 - .20 (.004 - .008) (NOTE 2)
1.90 (.074) REF
A1
S6 SOT-23 0401
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LT1806/LT1807
PACKAGE DESCRIPTIO
0.007 (0.18) 0.021 0.006 (0.53 0.015)
* DIMENSION DOES NOT INCLUDE MOLD FLASH, PROTRUSIONS OR GATE BURRS. MOLD FLASH, PROTRUSIONS OR GATE BURRS SHALL NOT EXCEED 0.006" (0.152mm) PER SIDE ** DIMENSION DOES NOT INCLUDE INTERLEAD FLASH OR PROTRUSIONS. INTERLEAD FLASH OR PROTRUSIONS SHALL NOT EXCEED 0.006" (0.152mm) PER SIDE
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Dimensions in inches (millimeters) unless otherwise noted.
MS8 Package 8-Lead Plastic MSOP
(Reference LTC DWG # 05-08-1660)
0.118 0.004* (3.00 0.102)
8
76
5
0.193 0.006 (4.90 0.15)
0.118 0.004** (3.00 0.102)
1 0.043 (1.10) MAX 0 - 6 TYP SEATING PLANE
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4 0.034 (0.86) REF
0.009 - 0.015 (0.22 - 0.38)
0.0256 (0.65) BSC
0.005 0.002 (0.13 0.05)
MSOP (MS8) 1100
LT1806/LT1807
PACKAGE DESCRIPTIO
0.010 - 0.020 x 45 (0.254 - 0.508) 0.008 - 0.010 (0.203 - 0.254) 0- 8 TYP
0.014 - 0.019 (0.355 - 0.483) TYP *DIMENSION DOES NOT INCLUDE MOLD FLASH. MOLD FLASH SHALL NOT EXCEED 0.006" (0.152mm) PER SIDE **DIMENSION DOES NOT INCLUDE INTERLEAD FLASH. INTERLEAD FLASH SHALL NOT EXCEED 0.010" (0.254mm) PER SIDE
0.016 - 0.050 (0.406 - 1.270)
Information furnished by Linear Technology Corporation is believed to be accurate and reliable. However, no responsibility is assumed for its use. Linear Technology Corporation makes no representation that the interconnection of its circuits as described herein will not infringe on existing patent rights.
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Dimensions in inches (millimeters) unless otherwise noted.
S8 Package 8-Lead Plastic Small Outline (Narrow .150 Inch)
(Reference LTC DWG # 05-08-1610)
0.189 - 0.197* (4.801 - 5.004) 8 7 6 5
0.228 - 0.244 (5.791 - 6.197)
0.150 - 0.157** (3.810 - 3.988)
1
2
3
4
0.053 - 0.069 (1.346 - 1.752)
0.004 - 0.010 (0.101 - 0.254)
0.050 (1.270) BSC
SO8 1298
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LT1806/LT1807
TYPICAL APPLICATIO
FET Input, Fast, High Gain Photodiode Amplifier Figure 10 shows a fast, high gain transimpedance amplifier applied to a photodiode. A JFET buffer is used for its extremely low input bias current and high speed. The LT1097 and 2N3904 keep the JFET biased at IDSS for zero offset and lowest voltage noise. The JFET then drives the LT1806, with RF closing the high speed loop back to the JFET input and setting the transimpedance gain. C4 helps improve the phase margin of the fast loop. Output voltage noise density was measured as 9nV/Hz with RF short circuited. With RF varied from 100k to 1M, total output
SIEMENS/ INFINEON SFH213FA PHOTODIODE VS-
RELATED PARTS
PART NUMBER LT1395 LT1399 LT1632/LT1633 LT1809/LT1810 DESCRIPTION 400MHz Current Feedback Amplifier Triple 300MHz Current Feedback Amplifier COMMENTS 800V/s Slew Rate, Shutdown 0.1dB Gain Flatness to 150MHz, Shutdown
Dual/Quad 45MHz, 45V/s Rail-to-Rail Input and Output Amplifiers High DC Accuracy 1.35mV VOS(MAX), 70mA Output Current, Max Supply Current 5.2mA/Amp Single/Dual 180MHz Input and Output Rail-to-Rail Amplifiers 350V/s Slew Rate, Shutdown, Low Distortion - 90dBc at 5MHz
18067f LT/LCG 1200 4K * PRINTED IN USA
24
Linear Technology Corporation
1630 McCarthy Blvd., Milpitas, CA 95035-7417
(408)432-1900 q FAX: (408) 434-0507 q www.linear-tech.com
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noise was below 1mVRMS measured over a 10MHz bandwidth. Table 4 shows results achieved with various values of RF and Figure 11 shows the time domain response with RF = 499k.
Table 4. Results Achieved for Various RF, 1.2V Output Step
RF 100k 200k 499k 1M
VS+ RF C4 3pF
10% to 90% RISE TIME 64ns 94ns 154ns 263ns
-3dB BANDWIDTH 6.8MHz 4.6MHz 3MHz 1.8MHz
2N5486 R1 10M R2 1M VS+ 3 C1 100pF 6 R3 10k 2N3904 C3 0.1F R4 2.4k VS- R5 33 2
* VS+
- +
7 LT1806 6 49.9 VOUT 50
18067 F10
3
+ -
7 LT1097
4 VS-
2
4 VS-
C2 2200pF
*ADJUST PARASITIC CAPACITANCE AT RF FOR DESIRED RESPONSE CHARACTERISTICS VS = 5V
Figure 10. Fast, High Gain Photodiode Amplifier
100mV/DIV
200ns/DIV
18067 F11
Figure 11. Step Response with RF = 499k
(c) LINEAR TECHNOLOGY CORPORATION 2000

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